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Radiation phase control system for a WIFI and
BLUETOOTH antenna array using phase shifters
1
Escuela Superior Politécnica de Chimborazo, Riobamba, Ecuador
RESUMEN
Este artículo presenta un sistema para controlar el
ángulo de sonido y cambiar rápidamente los patrones
de radiación de antenas WiFi y Bluetooth mediante la
modificación del desfase en un conjunto de antenas de
parche. El sistema incorpora un proceso de desfase para
lograr la formación de haz, lo que mejora la intensidad
de la señal en las ubicaciones deseadas y reduce el ruido
en áreas no deseadas. Esto implica el diseño de antenas
de parche con mediciones precisas, la instalación de una
unidad de control para ajustar el desfase y la prueba de
su funcionamiento en entornos reales y simulados. Las
mediciones se realizaron en un patrón circular, cubriendo
un área de 180 grados con 30 puntos, a intervalos de 6
grados, en una cámara anecoica. Se utilizó un voltaje
de 3 V para determinar el desfase entre mediciones sin
desfasador. Los resultados mostraron que sin desfasador,
se encontró un valor mínimo de -25,25 dB, mientras
que, con los diferentes voltajes, se obtuvo un valor de
-25,29 dB a 3 V, lo que indica un desfase aproximado
de 12 grados en comparación con las mediciones sin
desfasador. Los datos muestran cambios significativos
en la cobertura de la señal, el consumo de energía y
una mejora en el rendimiento del sistema. Los hallazgos
resaltan el potencial de este enfoque para su uso en
hogares inteligentes, dispositivos IoT y otros sistemas
de comunicación inalámbrica que requieren patrones de
radiación flexibles.
Palabras Clave: Microrred (MG), Costo de energía
(COE), Red eléctrica, HOMER Pro, Optimización
energética.
Sistema de control de fase de radiación para un conjunto de antenas
WIFI y BLUETOOTH mediante desplazadores de fase
Fecha de Recepción: 02 Julio 2025 · Fecha de Aceptación: 14 Mayo 2026 · Fecha de Publicación: 30 Julio 2026
ABSTRACT
This article presents a system for controlling the angle
of sound and rapidly changing the radiation patterns of
WiFi and Bluetooth antennas by modifying the phase
shift in a patch antenna array. The system incorporates
a phase shifting process to achieve beamforming,
which improves signal strength in desired locations
and reduces noise in undesired areas. This involves
designing patch antennas with precise measurements,
installing a control unit to adjust the phase shift, and
testing their operation in both real and simulated
environments. Measurements were made in a circular
pattern, covering a 180- degree area with 30 points,
at 6-degree intervals, in an anechoic chamber. A
voltage of 3 V was used to determine the phase shift
between measurements without a phase shifter. The
results showed that without a phase shifter, a minimum
value of -25.25 dB was found, while with the different
voltages, a value of -25.29 dB was obtained at 3 V,
indicating an approximate phase shift of 12 degrees
compared to measurements without a phase shifter.
The data show significant changes in signal coverage,
power utilization, and an improvement in system
performance. The findings highlight the potential of
this approach for use in smart homes, IoT devices, and
other wireless communication systems that require
flexible radiation patterns.
Keywords: Adaptive radiation patterns, Patch antenna
beamforming, Phase shift control, Wireless signal
coverage, IoT and smart home communications.
María Díaz
1
Dayana Pilco
3
mariac.diaz@espoch.edu.ec
dayana.pilco@espoch.edu.ec
Ana Ortega
2
José Samaniego
4
ana.ortegau6@espoch.edu.ec
enrique.samaniego@espoch.edu.ec
iD
Ronny Toctaquiza
5
ronny.toctaquiza@espoch.edu.ec
REVISTA PERSPECTIVAS
VOL. 8, N˚2 / JULIO - DICIEMBRE 2026 / e-ISSN: 266-6688
https://doi.org/10.47187/perspectivas.8.2.246
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The increasing use of wireless communication
systems has made technologies such as WiFi
and Bluetooth essential elements for modern
applications, ranging from IoT devices to smart
home networks [1]. At the core of these systems,
antennas play a critical role in determining
signal coverage, efficiency, and overall system
performance [2]. Patch antennas have become a
preferred solution due to their compact size, ease
of fabrication, and excellent performance at high
frequencies [3].
The main problem with WIFI and BLUETOOTH
systems is that they are manufactured to emit
signals in all directions. These are omnidirectional
antennas, which causes power loss by radiating
Fig. 1. Phase control system diagram
energy in undesired directions [4], generate
interfaces with other devices in the same band and
lack directional control of the radiation pattern,
limiting efficiency and range [5]. For this reason,
the implementation of a phase shifter in systems
with patch antenna arrays allows the radiation
pattern to be modified to direct the signal in
a specific direction, improving quality and
efficiency [6].
The integration of phase-shifting mechanisms into
antenna arrays enables advanced beamforming
capabilities. By controlling the phase of signals
at individual elements of an antenna array, it is
possible to dynamically steer the beam in desired
directions and suppress interference in undesired
areas. This approach significantly improves
spatial coverage and spectral efficiency of wireless
networks [7] [8].
Omnidirectional antennas, common in routers
and IoT devices, offer wide coverage but with
lower gain, while patch antennas, with a low
profile and directional pattern, are ideal for
WiFi systems (2.4 GHz and 5 GHz) in our case
in 2.4GHz and Bluetooth, especially in compact
devices such as wearables and advanced routers
with beamforming. This work seeks to design
and implement a dynamic phase control system to
modify in real time the radiation patterns of patch
antennas, using phase shifters based on varactors
or MEMS for reactive control and digital methods
with FPGAs for greater precision, thus optimizing
the signal performance [9].
II. Methodology
A. System architecture
The system consists of four main interconnected
modules: signal generation, dividers, phase
shifters and patch antennas. Each module has a
specific purpose in the design and control of the
system radiation pattern as shown in Fig. 1.
The function of each component is detailed below:
1. Signal generation: generate the carrier signal
at the 2.4GHz operating frequency for WIFI
and Bluetooth. For its implementation, a high-
precision signal generator capable of maintaining
stability in frequency and amplitude is used.
2. Divisors: three 1 to 2 dividers are used in an
electrical circuit designed to divide an input voltage
into two proportional output voltages, but with a
1:2 ratio. This means that the output signal has a
voltage that is half the input voltage in one case, or
double in another, depending on the configuration
of the divider. It is a concept commonly used in
electronic applications to reduce or increase the
voltage level in a signal.
3. Phase shifter circuit: The objective is to adjust
the phase of the signal arriving at each element
of the antenna array, thus modifying the radiation
pattern. In the implementation, the JSPHS/2484
component is used as a phase shifter. This device
will allow precise control of the phase of the
I. Introduction
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signal at each antenna in the array. The phase
shifters will receive regulated signals from the
driver circuit and will adjust their phase according
to the established values to achieve the desired
directivity.
4. Antenna Patch: the objective is to radiate the
adjusted signals with the desired pattern, adapting
the system to the operating frequency of WIFI and
Bluetooth. For this purpose, a patch antenna array
will be used, designed to work in the 2.4 GHz
band. The signals whose phase has been adjusted
by means of the JSPHS-2484 phase shifters will be
fed to the antenna, allowing the radiation pattern
to be dynamically modified by varying the phase
shifter between the array elements. This array
design will be optimized to maximize directivity
and minimize losses, ensuring good performance
in the wireless applications in which it will be
worked.
B. Signal divider simulation
Fig. 2 shows a 1-to-2 power splitter, which is a
passive component used in RF and microwave
systems. This type of splitter takes an input signal
at port 3 and distributes it into two output signals
of equal magnitude at ports 1 and 2. For this
research, a Wilkinson splitter was implemented. It
is composed of 50-ohms transmission lines (TL13
and TL14) to carry the signal, and an additional
transmission line (TL22) helps to achieve the
impedance matching and splitting. A 100-ohm
resistor (R1) provides isolation between the output
ports. When the RF signal enters the TermG
connector, it is split into two signals of equal
power at the junction of TL13 and TL14. Resistor
R1 plays a crucial role by isolating the output
ports, preventing interference between the signals
and ensuring good signal quality at each port.
Furthermore, the power splitter is designed
to maintain 50-ohm impedance for all ports,
ensuring efficient power transfer and minimizing
signal reflections. The two split signals are
delivered through the connectors. This splitter
stands out for its good impedance matching, high
isolation between ports, and equal power splitting,
making it a valuable tool in applications such as
wireless communication systems, radars, and
measurement equipment.
However, it is important to consider that power
splitter has a limited bandwidth and its power is
limited by resistance. The simulation of this power
splitter was performed in the ADS (Advanced
Design System) program, a software widely used
in RF and microwave circuit design.
Fig. 2. Power divider simulation
Fig. 3 shows the frequency response of the
Wilkinson power splitter presented before. The
blue curve (S1,1) represents the power reflected at
the input port (TermG), indicating good impedance
matching across the frequency range, as it remains
below -20 dB. The red (S1,2) and purple (S1,3)
curves represent the power transmitted to the
output ports (TermG2 and TermG3), respectively.
It is observed that both curves overlap and stay
around -3 dB, indicating an equal power split
between the two output ports. Furthermore,
the flatness of these curves suggests a good
performance of the splitter over a wide frequency
range. In summary, the graph confirms that the
Wilkinson splitter splits the input power equally
between the output ports, with good impedance
matching and consistent performance over the
frequency range analyzed.
Fig. 3. Power divider radiation pattern
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C. Simulation of the patch antenna
Fig. 4 shows the design of a rectangular microstrip
antenna, modeled on a two-dimensional plane
with specific dimensions. The overall width of
the design is 66 mm, while its height reaches 61
mm. The design incorporates a 4 mm wide and
36 mm long feed line that connects to the main
radiating zone. This radiating zone, with a height
of 31 mm, includes cut-out corners, indicating a
possible optimization aimed at improving the
antenna performance and its adaptation to the
intended operating frequency. In addition, the
feed port, identified as “Port1”, is set as the entry
point for the excitation signal. This design seeks
to ensure a balance between the antenna’s physical
dimensions and its electromagnetic performance,
meeting coupling and efficiency requirements.
Fig. 5 shows the magnitude diagram of the
reflection coefficient (S11) in dB of an antenna
evaluated in the frequency range of 2.00 GHz to
3.00 GHz. This graph was generated by simulation,
using specialized software for electromagnetic
analysis.
The horizontal axis of the graph shows the
frequency in GHz, while the vertical axis shows
the reflection coefficient in dB. A value of S11
less than -10 dB indicates that most of the power
transmitted from the feed port is radiated by
the antenna, representing good performance in
impedance matching. The main result shown
in this graph reveals that the antenna operates
efficiently in a frequency range delimited by the
points where S11 crosses the -10 dB threshold.
In this case, it is observed that the frequency
range is between 2.25 GHz and 2.55 GHz, which
determines an operating bandwidth of 300 MHz.
This range is suitable for applications that require
good radiation in the specified band.
Additionally, the minimum point of the reflection
coefficient reaches a value of approximately -42
dB at a frequency of 2.45 GHz, which represents
the resonance frequency of the antenna. At
this frequency, the power coupling is optimal,
maximizing radiation efficiency.
Fig. 4. Patch Antenna
Fig. 5. Reflection coefficient (S11)
Fig. 6 shows the radiation pattern of the patch
antenna operating at 2.4 GHz, a frequency used in
WiFi and Bluetooth systems. The horizontal axis
represents the Theta angle [°], while the vertical
axis shows the magnitude of the electric field in
decibels (dB). The graph presents two curves:
• The blue curve: represents the principal
component of the electric field, E-theta. A deep
“null”, i.e., a drastic drop in intensity, is observed
at the center of the diagram (0 degrees). This
indicates that the antenna does not radiate a signal
in that direction.
• The red curve: represents the E-phi component,
showing the radiation in a polarization orthogonal
to that of the principal component (E-theta). This
curve complements the information in the blue
curve and helps to understand the antenna’s full
radiation pattern.
Together, these curves reveal that the patch
antenna is directional. Instead of radiating energy
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evenly in all directions, it concentrates radiation
to the sides and forward, with areas of lower
radiation in certain directions, such as the center.
This directionality is a key feature of antennas
designed for applications such as WiFi networks
and Bluetooth systems, where efficient coverage
is sought towards a specific target area. By
concentrating energy in a preferential direction,
communication efficiency is improved and
interference in other directions is reduced. The
radiation pattern shown in the image confirms this
directionality, explaining why patch antennas are
a common choice in wireless devices that require
a defined range and coverage.
Fig. 6. Radiation pattern (S11) in Ansoft program
III. Results
A. Signal divider implementation
Fig. 7 presents the physical implementation of
the microstrip power signal divider, which is a
key component in RF and microwave circuits for
the 1700/2100 MHz AWS bands. The rectangular
shape of the conductive patch and the microstrip
lines determine the impedance matching and
splitting characteristics. The dielectric material
(the yellow part) provides mechanical support
and electrical properties for the operation of the
divider. The SMA connector allows connection to
other circuits or measurement instruments. This
divider works by dividing the high frequency
current entering through the connector into
two equal currents that propagate through the
microstrip lines to the outputs. The geometry of
the divider is designed to ensure that the power
is divided equally and that the impedance is kept
matched to avoid signal reflections.
Fig. 7. Physical Implementation of Power Divider
In addition to its primary function of power
splitting, this splitter also plays a crucial role in the
realization of antenna arrays. By splitting the input
signal and feeding multiple antennas, the splitter
allows for the creation of arrays that direct the
signal propagation in a specific direction. When
designing antenna arrays, splitter characteristics
such as power splitting, impedance matching,
and isolation between outputs must be carefully
considered to achieve the desired radiation pattern
and directivity.
C. Signal divider validation
As a first step to verify the performance of the
implemented power splitter, measurements were
made with a vector network analyzer (VNA),
connecting two 50-ohm coaxial cables to ports 1
and 2 of the divider, while a load resistor at the
input as shown in Fig. 8.
B. Signal divider implementation
Fig. 7 presents the physical implementation of
the microstrip power signal divider, which is a
key component in RF and microwave circuits for
the 1700/2100 MHz AWS bands. The rectangular
shape of the conductive patch and the microstrip
lines determine the impedance matching and
splitting characteristics. The dielectric material
(the yellow part) provides mechanical support
and electrical properties for the operation of the
divider. The SMA connector allows connection to
other circuits or measurement instruments. This
divider works by dividing the high
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Using this configuration, Fig. 9 presents the
response of the implemented divider measured
using a Vector Network Analyzer (VNA) model
E5071C. The main trace represents the reflection
coefficient (S11) of the voltage divider as a function
of frequency, verified by connecting a load
resistor at the divider input. Marker 1 indicates a
minimum of -10.135 dB at 2.45 GHz, confirming
the correct impedance matching and resonance at
this frequency. This result validates the previous
simulation in ADS and guarantees efficient filter
operation at the desired frequency.
At the same time, Fig. 10 shows the reflection
coefficient (S12) of the voltage divider as a function
of frequency. For verification, a load resistor was
connected to the input of the divider. Marker 1
indicates a minimum of -7.2362 dB at 2.45 GHz,
confirming proper impedance and resonance
matching at this frequency. This result validates
the previous simulation in ADS and ensures
efficient filter operation at the desired frequency.
Fig. 9. Reflection coefficient (S11) of the divider input.
Fig. 10. Reflection coefficient (S12) of the divider input.
Second step of validation continues with the
connections of the splitter as shown in Fig. 11,
where the input and output 2 are connected to the
VNA, while a 50-ohm load resistor was placed on
output 1.
Under this measurement configuration, Fig. 12
shows the reflection coefficient (S11) of the voltage
divider as a function of frequency. Marker 1
indicates a minimum of -7.6613 dB at 2.45 GHz,
confirming proper impedance and resonance
matching at this frequency. This result validates
the previous simulation in ADS and ensures
efficient filter operation at the desired frequency.
Fig. 11. Power divider with load resistor at output 1
Fig. 12. Reflection coefficient (S11) of output 1 of the divider.
Fig. 8. Power divider with load resistor at input
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In addition, Fig. 13 shows the reflection coefficient
(S12) of the signal divider as a function of
frequency, when a load resistor was connected
to output 1 of the divider. Marker 1 indicates a
minimum of -5.1342 dB at 2.45 GHz, confirming
proper impedance and resonance matching at
this frequency. This result validates the previous
simulation in ADS and ensures efficient filter
operation at the desired frequency.
Third step of validation continues with the
connections of the splitter as shown in Fig. 14,
where the input and output 1 are connected to the
VNA, while a 50-ohm load resistor was placed on
output 2.
Fig. 14. Power divider with load resistor at output 2
Results plotted in Fig. 15 show the reflection
coefficient (S11) of the signal divider as a function
of frequency. Marker 1 indicates a minimum
Fig. 15. Reflection coefficient (S11) of output 2 of the divider.
of -18.018dB at 2.45 GHz, confirming proper
impedance and resonance matching at this
frequency. This result validates the previous
simulation in ADS and ensures efficient filter
operation at the desired frequency.
Fig. 13. Reflection coefficient (S11) of output 1 of the divider.
D. Implementation of patch antenna
In Fig. 17, the physical implementation of the patch
antenna is shown. At this stage, the dimensions and
features of the original design are materialized,
including the radiating patch, feed line, and signal
connector. Manufacturing precision and choice of
materials are key factors to ensure that the real
antenna reproduces the simulated performance,
meeting the stated coupling and efficiency
requirements.
Fig. 16. Reflection coefficient (S12) of output 2 of the divider.
Also, Fig. 16 shows the reflection coefficient (S12)
of the voltage divider as a function of frequency.
Marker 1 indicates a minimum of -5.0511 dB at
2.45 GHz, confirming proper impedance and
resonance matching at this frequency. This result
validates the previous simulation in ADS and
ensures efficient filter operation at the desired
frequency.
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Fig. 18. Patch antenna radiation pattern
E. Measurements with antenna array
The initial measurements were made using
the antenna matrix as shown in Fig. 19
within an anechoic chamber. To obtain a
precise representation of the radiation pattern,
measurements were taken every six degrees around
180 degrees, giving a total of 30 measurements to
verify the proper operation and observe the highest
radiation that occurs in the front of the matrix.
The remaining 30 points of the 360 degrees
measurements were made later. This methodology
allowed a detailed capture of the system response
in several directions, facilitating the visualization
and analysis of radiation behavior.
Fig. 19. Antenna arrangement within an anechoic chamber.
Fig. 20 shows the radiation pattern of the antenna
array obtained by measurements at different
angles, particularly every 6 degrees. It is observed
that the energy is mainly concentrated in one
sector of the plane, spanning approximately 0
to 180 degrees on the right side. This radiation
pattern confirms that the antenna array is working
correctly, since the radiation is not distributed
uniformly in all directions, but is concentrated in
a specific sector. The shape and direction of the
main and secondary lobes, as well as the symmetry
of the pattern, are important characteristics that
are analyzed to evaluate the performance of the
array. In addition, the intensity of the radiation at
each angle provides valuable information about
the efficiency and directivity of the array.
Fig. 18 shows the response of a patch antenna,
combining the previous simulation performed
in Ansoft with the physical verification of its
operation using the VNA. The main trace, “Tr1
S11 Log Mag 10.00dB/ Ref 0.000dB [F1]”, shows
the reflection coefficient (S11) of the antenna as a
function of frequency. It is observed that marker
3 indicates a minimum of -27.499 dB in S11 at
2.445 GHz, confirming a good impedance and
resonance match at this frequency. This result
validates the previous simulation in Ansoft and
ensures that the antenna operates efficiently at the
desired frequency. The graph covers a range from
1 GHz to 5 GHz, with an IFBW (Intermediate
Frequency Bandwidth) of 70 kHz and a span of
2 GHz.
Fig. 17. Physical implementation of Patch Antenna.
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Fig. 20. Radiation pattern of the first measurement in a specific
direction.
The radiation pattern presents two lines: one in
blue, corresponding to the measurements made
with 10 volts, and another in red, representing
the measurements made with 5 volts. This
differentiation allows comparing the behavior
of the array under different power conditions,
which is crucial to evaluate its performance and
adaptation to different operating scenarios.
This radiation pattern is critical to determining
whether the array meets the requirements
of the desired application, such as wireless
communications or radar systems. Consequently,
this pattern validates the correct implementation
of the antenna array and its capability for
applications requiring directionality.
F. Partial measurements for radiation pattern
calculation
The measurements were made with an antenna
matrix consisting of four patch antennas. For this
study, different voltages were assigned to each
gear lever to analyze the matrix phase change.
During this validation, four voltage sources were
used and three different measurements were done.
Results obtained are plotted in Fig. 21, where
these are compared to the original measurement
(blue color), which was acquired without the
implementation of the gear lever.
In Fig. 21, the red curve corresponds to a voltage
of 3 Volts, where it is observed that there is a
phase shift with respect to the original signal. This
information allowed a comparison between the
radiation diagrams generated with the different
voltages applied.
Fig. 21. Radiation Patter at different voltage in the “shifter”.
When performing the comparative analysis
between the measurements with variation in the
gear levers and the original measurement, it is
observed that the original measurement has a
greater power compared to the measurements
with variation. This is due to the dispersion losses
caused by the connectors, cables and gear levers,
which generate a phase shift in the matrix, but
with a significant attenuation of the signal
G. Linear measurement every 10 cm
Fig. 22 shows a linear measurement performed with
an antenna array. To perform this measurement,
values were recorded over a distance extending
from the center point to 110 centimeters, with
a variation of 10 centimeters per point. This
measurement was performed in both directions,
i.e., from the center toward the positive (right) and
negative (left) side of the central reference.
This process allowed obtaining a detailed
representation of the distribution of the signal or
property measured in a symmetrical range around
the center of the antenna array configuration.
Taking data in both directions facilitates a more
complete analysis of the signal propagation or
behavior as a function of distance from the source,
which is essential for evaluating characteristics
such as directivity, coverage, or uniformity of the
antenna system.
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The measurements were made in an anechoic
chamber, which allowed to register radiation
patterns with high precision, eliminating external
reflections that could interfere with the real
characterization of the antenna arrangement.
This methodology guarantees The measurements
were made in an anechoic chamber, which
allowed to register radiation patterns with high
precision, eliminating external reflections that
could interfere with the real characterization
of the antenna arrangement. This methodology
guarantees that the results obtained are
representative of the electromagnetic behavior of
the system in controlled conditions. An angular
shift of approximately 12 degrees was observed in
the radiation pattern when different voltage levels
(3V, 6V, 9V, 12V, and 15V) were applied to the
phase shifters, compared to the reference curve
without a phase shifter. This result validates the
correct operation of the phase control system and
its ability to steer the main lobe of the beam in a
specific direction. The system proved effective for
adaptive wireless communications applications,
allowing dynamic modification of the antenna
array’s radiation pattern. This feature is especially
useful in environments such as smart homes or
IoT devices, where signal targeting is required to
improve coverage and reduce interference.
[1] C. Systems, “WiFi technology overview,” Tech.
Rep., 2016. [Online]. Available: https://www.
cisco.com
[2] D. M. Pozar, Microwave Engineering, 3rd ed.
Wiley, 2005.
[3] C. A. Balanis, “Antenna theory: Analysis and
design,” 2016.
[4] G. V. Tsoulos, Adaptive Antennas for Wireless
Communications. Wiley, 2001.
[5] M. A. Hossain and M. T. Islam, “Compact and
high-performance microstrip patch antennas
for IoT applications,” Sensors, vol. 20, no. 8, p.
2272, 2020.
[6] T. Lim, S. Gao, and T. Loh, “Design of
beam-steering microstrip array antennas using
The radiation pattern obtained from measurements
made with the antenna array in a linear
configuration, spanning from 0 to 110 centimeters
in both the positive and negative directions, is
shown in Fig. 23. These measurements were made
at 3 volts and without a shifter, which allowed a
detailed phase shift of 12 degrees to be observed
in the signals. The blue curve represents the
reference, that is, the measurements made without
the use of a phase shifter. The red curve represents
the signal generated from 3 volts.
This graph clearly visualizes the behavior of the
antenna array under different power conditions. A
constant angular shift of the radiation pattern is
observed in the curve where a voltage was applied,
compared to the reference curve.
Specifically, a phase shift of approximately 12
degrees is identified in the curves corresponding
to the different voltage levels with respect to the
curve without a shifter, confirming the expected
effect of phase control on the main lobe direction.
Fig. 23. Linear measurement with an antenna array.
VI. References
V. Conclusions
Fig. 22. Linear measurement with an antenna array within an
anechoic chamber.
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phase shifters,” IEEE Transactions on Antennas
and Propagation, vol. 63, no. 7, pp. 3079–3086,
2015.
[7] I. S. Association, IEEE 802.11ax: High-Effi-
ciency WLAN, Std., 2021.
[8] P. Goel and K. J. Vinoy, “A low-cost phased
array antenna integrated with phase shifters,”
Progress In Electromagnetics Research B, vol.
30, pp. 255–277, 2011.
[9] A. Karmakar, B. Roy, and A. K. Bhattacharjee,
“Mems- based monolithic phased array using
3-bit switched-line phase shifter,” Advanced
Electromagnetics, 2025. [Online]. Available:
https://aemjournal.org/index.php/AEM/article/
view/520
[10] C. Paz, “Diseño y simulación de un sistema ra-
diante basado en antenas yagi-uda que imple-
mente la técnica de beamforming a una frecuen-
cia de operación de 6 GHz,” Master’s thesis,
Repositorio EPN, 2022, s.l.
[11] M. Amri and F. Echouchene, “Phased array
antenna structure based on novel 6-bit phase
shifter for WiFi communication systems,” In-
ternational Review of Electrical and Computer
Engineering, vol. 15, no. 1, pp. 10– 18, 2025.
